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1 LTC2420 20-bit m power no latency ds tm adc in so-8 n weight scales n direct temperature measurement n gas analyzers n strain gauge transducers n instrumentation n data acquisition n industrial process control n 4-digit dvms no latency ds is a trademark of linear technology corporation. microwire is a trademark of national semiconductor corporation. total unadjusted error (3v supply) , ltc and lt are registered trademarks of linear technology corporation. n 20-bit adc in so-8 package n 8ppm inl, no missing codes at 20 bits n 4ppm full-scale error n 0.5ppm offset n 1.2ppm noise n digital filter settles in a single cycle. each conversion is accurate, even after an input step n fast mode: 16-bit noise, 12 bits tue at 100sps n internal oscillatorno external components required n 110db min, 50hz/60hz notch filter n reference input voltage: 0.1v to v cc n live zeroextended input range accommodates 12.5% overrange and underrange n single supply 2.7v to 5.5v operation n low supply current (200 m a) and auto shutdown n pin compatible with 24-bit ltc2400 the ltc ? 2420 is a micropower 20-bit a/d converter with an integrated oscillator, 8ppm inl and 1.2ppm rms noise that operates from 2.7v to 5.5v. it uses delta-sigma technology and provides a digital filter that settles in a single cycle for multiplexed applications. through a single pin, the LTC2420 can be configured for better than 110db rejection at 50hz or 60hz 2%, or it can be driven by an external oscillator for a user-defined rejection frequency in the range 1hz to 800hz. the internal oscillator requires no external frequency setting components. the converter accepts any external reference voltage from 0.1v to v cc . with its extended input conversion range of C12.5% v ref to 112.5% v ref , the LTC2420 smoothly resolves the offset and overrange problems of preceding sensors or signal conditioning circuits. the LTC2420 communicates through a flexible 3-wire digital interface which is compatible with spi and microwire tm protocols. features descriptio u applicatio s u typical applicatio u v cc f o v ref sck v in sdo 1 2 3 4 8 7 6 5 gnd cs reference voltage 0.1v to v cc analog input range 0.12v ref to 1.12v ref = internal osc/50hz rejection = external clock source = internal osc/60hz rejection 3-wire spi interface 1 f 2.7v to 5.5v LTC2420 2420 ta01 v cc input voltage (v) 0 error (ppm) 2 6 10 2.0 2420 g01 ? ? 0 4 8 ? ? ?0 0.5 1.0 1.5 2.5 v cc = 3v v ref = 2.5v t a = 55 c, 45 c, 25 c, 90 c
2 LTC2420 parameter conditions min typ max units resolution (no missing codes) 0.1v v ref v cc , (note 5) l 20 bits integral nonlinearity v ref = 2.5v (note 6) l 4 10 ppm of v ref v ref = 5v (note 6) l 8 20 ppm of v ref integral nonlinearity (fast mode) v ref = 5v, v ref = 2.5v, 100 samples/second, f o = 2.048mhz l 40 250 ppm of v ref offset error 2.5v v ref v cc l 0.5 10 ppm of v ref offset error (fast mode) 2.5v < v ref < 5v, 100 samples/second, f o = 2.048mhz 3 ppm of v ref offset error drift 2.5v v ref v cc 0.04 ppm of v ref / c full-scale error 2.5v v ref v cc l 4 10 ppm of v ref full-scale error (fast mode) 2.5v < v ref < 5v, 100 samples/second, f o = 2.048mhz 10 ppm of v ref full-scale error drift 2.5v v ref v cc 0.04 ppm of v ref / c total unadjusted error v ref = 2.5v 8 ppm of v ref v ref = 5v 16 ppm of v ref output noise v in = 0v (note 13) 6 m v rms output noise (fast mode) v ref = 5v, 100 samples/second, f o = 2.048mhz 20 m v rms normal mode rejection 60hz 2% (note 7) l 110 130 db normal mode rejection 50hz 2% (note 8) l 110 130 db power supply rejection, dc v ref = 2.5v, v in = 0v 100 db power supply rejection, 60hz 2% v ref = 2.5v, v in = 0v, (notes 7, 15) 110 db power supply rejection, 50hz 2% v ref = 2.5v, v in = 0v, (notes 8, 15) 110 db order part number consult factory for military grade parts. s8 part marking (notes 1, 2) supply voltage (v cc ) to gnd ....................... C 0.3v to 7v analog input voltage to gnd ....... C 0.3v to (v cc + 0.3v) reference input voltage to gnd .. C 0.3v to (v cc + 0.3v) digital input voltage to gnd ........ C 0.3v to (v cc + 0.3v) digital output voltage to gnd ..... C 0.3v to (v cc + 0.3v) operating temperature range LTC2420c ............................................... 0 c to 70 c LTC2420i ............................................ C 40 c to 85 c storage temperature range ................. C 65 c to 150 c lead temperature (soldering, 10 sec).................. 300 c t jmax = 125 c, q ja = 130 c/w LTC2420cs8 LTC2420is8 2420 2420i the l denotes specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. (notes 3, 4) absolute m axi m u m ratings w ww u package/order i n for m atio n uu w co n verter characteristics u 1 2 3 4 8 7 6 5 top view f o sck sdo cs v cc v ref v in gnd s8 package 8-lead plastic so
3 LTC2420 symbol parameter conditions min typ max units v ih high level input voltage 2.7v v cc 5.5v l 2.5 v cs, f o 2.7v v cc 3.3v 2.0 v v il low level input voltage 4.5v v cc 5.5v l 0.8 v cs, f o 2.7v v cc 5.5v 0.6 v v ih high level input voltage 2.7v v cc 5.5v (note 9) l 2.5 v sck 2.7v v cc 3.3v (note 9) 2.0 v v il low level input voltage 4.5v v cc 5.5v (note 9) l 0.8 v sck 2.7v v cc 5.5v (note 9) 0.6 v i in digital input current 0v v in v cc l C10 10 m a cs, f o i in digital input current 0v v in v cc (note 9) l C10 10 m a sck c in digital input capacitance 10 pf cs, f o c in digital input capacitance (note 9) 10 pf sck v oh high level output voltage i o = C 800 m a l v cc C 0.5 v sdo v ol low level output voltage i o = 1.6ma l 0.4 v sdo v oh high level output voltage i o = C 800 m a (note 10) l v cc C 0.5 v sck v ol low level output voltage i o = 1.6ma (note 10) l 0.4 v sck i oz high-z output leakage l C10 10 m a sdo digital i puts a d digital outputs u u symbol parameter conditions min typ max units v cc supply voltage l 2.7 5.5 v i cc supply current conversion mode cs = 0v (note 12) l 200 300 m a sleep mode cs = v cc (note 12) l 20 30 m a power require e ts w u the l denotes specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. (note 3) the l denotes specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. (note 3) symbol parameter conditions min typ max units v in input voltage range (note 14) l C 0.125 ? v ref 1.125 ? v ref v v ref reference voltage range l 0.1 v cc v c s(in) input sampling capacitance 1 pf c s(ref) reference sampling capacitance 1.5 pf i in(leak) input leakage current cs = v cc l C 100 1 100 na i ref(leak) reference leakage current v ref = 2.5v, cs = v cc l C 100 1 100 na the l denotes specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. (note 3) a alog i put a d refere ce u u u u
4 LTC2420 the l denotes specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. (note 3) f eosc external oscillator frequency range 20-bit effective resolution l 2.56 307.2 khz 12-bit effective resolution l 2.56 2.048 mhz t heo external oscillator high period l 0.2 390 m s t leo external oscillator low period l 0.2 390 m s t conv conversion time f o = 0v l 130.86 133.53 136.20 ms f o = v cc l 157.03 160.23 163.44 ms external oscillator (note 11) l 20510/f eosc (in khz) ms f isck internal sck frequency internal oscillator (note 10) 19.2 khz external oscillator (notes 10, 11) f eosc /8 khz d isck internal sck duty cycle (note 10) 45 55 % f esck external sck frequency range (note 9) l 2000 khz t lesck external sck low period (note 9) l 250 ns t hesck external sck high period (note 9) l 250 ns t dout_isck internal sck 24-bit data output time internal oscillator (notes 10, 12) l 1.23 1.25 1.28 ms external oscillator (notes 10, 11) l 192/f eosc (in khz) ms t dout_esck external sck 24-bit data output time (note 9) l 24/f esck (in khz) ms t 1 cs to sdo low z l 0 150 ns t2 cs - to sdo high z l 0 150 ns t3 cs to sck (note 10) l 0 150 ns t4 cs to sck - (note 9) l 50 ns t kqmax sck to sdo valid l 200 ns t kqmin sdo hold after sck (note 5) l 15 ns t 5 sck set-up before cs l 50 ns t 6 sck hold after cs l 50 ns symbol parameter conditions min typ max units note 1: absolute maximum ratings are those values beyond which the life of the device may be impaired. note 2: all voltage values are with respect to gnd. note 3: all voltages are with respect to gnd. v cc = 2.7 to 5.5v unless otherwise specified. r source = 0 w . note 4: internal conversion clock source with the f o pin tied to gnd or to v cc or to external conversion clock source with f eosc = 153600hz unless otherwise specified. note 5: guaranteed by design, not subject to test. note 6: integral nonlinearity is defined as the deviation of a code from a straight line passing through the actual endpoints of the transfer curve. the deviation is measured from the center of the quantization band. note 7: f o = 0v (internal oscillator) or f eosc = 153600hz 2% (external oscillator). note 8: f o = v cc (internal oscillator) or f eosc = 128000hz 2% (external oscillator). note 9: the converter is in external sck mode of operation such that the sck pin is used as digital input. the frequency of the clock signal driving sck during the data output is f esck and is expressed in khz. note 10: the converter is in internal sck mode of operation such that the sck pin is used as digital output. in this mode of operation the sck pin has a total equivalent load capacitance c load = 20pf. note 11: the external oscillator is connected to the f o pin. the external oscillator frequency, f eosc , is expressed in khz. note 12: the converter uses the internal oscillator. f o = 0v or f o = v cc . note 13: the output noise includes the contribution of the internal calibration operations. note 14: for reference voltage values v ref > 2.5v the extended input of C 0.125 ? v ref to 1.125 ? v ref is limited by the absolute maximum rating of the analog input voltage pin (pin 3). for 2.5v < v ref 0.267v + 0.89 ? v cc the input voltage range is C 0.3v to 1.125 ? v ref . for 0.267v + 0.89 ? v cc < v ref v cc the input voltage range is C 0.3v to v cc + 0.3v. note 15: v cc (dc) = 4.1v, v cc (ac) = 2.8v p-p . ti i g characteristics u w
5 LTC2420 typical perfor a ce characteristics uw total unadjusted error (3v supply) negative input extended total unadjusted error (3v supply) input voltage (v) 0 error (ppm) 2 6 10 2.0 2420 g01 ? ? 0 4 8 ? ? ?0 0.5 1.0 1.5 2.5 v cc = 3v v ref = 2.5v t a = 55 c, 45 c, 25 c, 90 c input voltage (v) 0 error (ppm) 2 6 10 2.0 2420 g02 ? ? 0 4 8 ? ? ?0 0.5 1.0 1.5 2.5 v cc = 3v v ref = 2.5v t a = 55 c, 45 c, 25 c, 90 c input voltage (v) 0 ?0 ? ? 2 0.05 0.10 0.15 0.20 2420 g03 0.25 10 0.30 error (ppm) 6 ? ? 0 8 4 v cc = 3v v ref = 2.5v t a = 90 c t a = 25 c t a = 45 c t a = 55 c inl (3v supply) positive input extended total unadjusted error (3v supply) input voltage (v) 2.50 ?0 ? ? 2 2.55 2.60 2.65 2.70 2420 g04 2.75 10 2.80 error (ppm) 6 ? ? 0 8 4 v cc = 3v v ref = 2.5v t a = 55 c, ?5 c, 25 c, 90 c input voltage (v) 0 error (ppm) 2 6 10 4 2420 g05 ? ? 0 4 8 ? ? ?0 1 2 3 5 v cc = 5v v ref = 5v t a = 55 c, 45 c, 25 c, 90 c total unadjusted error (5v supply) inl (5v supply) input voltage (v) 0 error (ppm) 2 6 10 4 2420 g06 ? ? 0 4 8 ? ? ?0 1 2 3 5 v cc = 5v v ref = 5v t a = 55 c, 45 c, 25 c, 90 c negative input extended total unadjusted error (5v supply) input voltage (v) 0 ?0 ? ? 2 0.05 0.10 0.15 0.20 2420 g07 0.25 10 0.30 error (ppm) 6 ? ? 0 8 4 v cc = 5v v ref = 5v t a = 90 c t a = 25 c t a = 55 c t a = 45 c positive input extended total unadjusted error (5v supply) input voltage (v) 5.00 ?0 ? ? 2 5.05 5.10 5.15 5.20 2420 g08 5.25 10 5.30 error (ppm) 6 ? ? 0 8 4 v cc = 5v v ref = 5v t a = 45 c t a = 55 c t a = 25 c t a = 90 c offset error vs reference voltage reference voltage (v) 0 offset error (ppm) 90 120 150 4 2420 g09 60 30 0 1 2 3 5 v cc = 5v t a = 25 c
6 LTC2420 typical perfor a ce characteristics uw rms noise vs reference voltage offset error vs v cc reference voltage (v) 0 0 rms noise (ppm of v ref ) 10 20 30 40 50 60 1234 2420 g10 5 v cc = 5v t a = 25 c v cc (v) 2.7 ?0 offset error (ppm) ? 0 5 10 3.2 3.7 4.2 4.7 2420 g11 5.2 5.5 v ref = 2.5v t a = 25 c rms noise vs v cc v cc (v) 2.7 0 rms noise (ppm) 2.5 5.0 7.5 10.0 3.2 3.7 4.2 4.7 2420 g12 5.2 5.5 v ref = 2.5v t a = 25 c noise histogram rms noise vs code out offset error vs temperature code out (hex) 0 7fffff ffffff 0 rms noise (ppm) 1.25 2.50 3.75 5.00 2420 g14 v cc = 5v v ref = 5v v in = 0.3v to 5.3v t a = 25 c temperature ( c) ?5 ?0 offset error (ppm) ? 0 5 10 ?0 5 20 45 2420 g15 70 95 120 v cc = 5v v ref = 5v v in = 0v full-scale error vs temperature full-scale error vs v cc temperature ( c) ?5 ?0 full-scale error (ppm) ? 0 5 10 ?0 5 20 45 2420 g16 70 95 120 v cc = 5v v ref = 5v v in = 5v full-scale error vs reference voltage reference voltage (v) 0 150 full-scale error (ppm) 125 100 ?5 ?0 ?5 0 1234 2420 g17 5 v cc = 5v v in = v ref v cc (v) 2.7 ?0 full-scale error (ppm) ? 0 5 10 3.2 3.7 4.2 4.7 2420 g18 5.2 5.5 v ref = 2.5v v in = 2.5v t a = 25 c output code (ppm) 0 50 100 150 200 250 300 350 26 2420g13 ? 0 4 number of readings v cc = 5 v ref = 5 v in = 0
7 LTC2420 typical perfor a ce characteristics uw conversion current vs temperature sleep current vs temperature rejection vs frequency at v cc temperature ( c) ?5 supply current ( a) 220 20 2420 g19 190 170 ?0 5 45 160 150 230 210 200 180 70 95 120 v cc = 5.5v v cc = 4.1v v cc = 2.7v temperature ( c) ?5 0 supply current ( m a) 10 20 30 ?0 5 20 45 2420 g20 70 95 120 v cc = 2.7v v cc = 5v rejection vs frequency at v cc rejection vs frequency at v cc rejection vs frequency at v in rejection vs frequency at v in rejection vs frequency at v in rejection vs frequency at v in frequency at v cc (hz) 1 rejection (db) ?0 ?0 ?0 200 2420 g21 ?0 ?00 ?20 50 100 150 250 v cc = 4.1v v in = 0v t a = 25 c f o = 0 frequency at v cc (hz) 15200 120 rejection (db) 100 ?0 ?0 ?0 0 15250 15300 15350 15400 2420 g22 15450 15500 ?0 v cc = 4.1v v in = 0v t a = 25 c f o = 0 frequency at v cc (hz) 1 ?20 rejection (db) ?00 ?0 ?0 ?0 ?0 0 100 10k 1m 2420 g23 v cc = 4.1v v in = 0v t a = 25 c f o = 0 frequency at v in (hz) 1 120 rejection (db) 100 ?0 ?0 ?0 ?0 0 50 100 150 200 2420 g24 250 v cc = 5v v ref = 5v v in = 2.5v f o = 0 input frequency deviation from notch frequency (%) 128404812 rejection (db) 2420 g25 ?0 ?0 ?0 ?0 100 110 120 130 140 frequency at v in (hz) 15100 120 rejection (db) 100 ?0 ?0 ?0 ?0 0 15200 15300 15400 15500 2420 g26 v cc = 5v v ref = 5v v in = 2.5v f o = 0 sample rate = 15.36khz 2% input frequency 0 ?0 ?0 0 2420 f27 ?0 100 f s /2 f s 120 140 ?0 rejection (db)
8 LTC2420 typical perfor a ce characteristics uw inl vs output rate inl vs output rate resolution vs output rate output rate (hz) 0 7.5 resolution (bits) 20 22 75 2420 g30 18 16 25 50 100 24 t a = 25 c t a = 90 c t a = 45 c v cc = 5v v ref = 5v f o = external v cc (pin 1): positive supply voltage. bypass to gnd (pin 4) with a 10 m f tantalum capacitor in parallel with 0.1 m f ceramic capacitor as close to the part as possible. v ref (pin 2): reference input. the reference voltage range is 0.1v to v cc . v in (pin 3): analog input. the input voltage range is C 0.125 ? v ref to 1.125 ? v ref . for v ref > 2.5v the input voltage range may be limited by the pin absolute maxi- mum rating of C 0.3v to v cc + 0.3v. gnd (pin 4): ground. shared pin for analog ground, digital ground, reference ground and signal ground. should be connected directly to a ground plane through a mini- mum length trace or it should be the single-point-ground in a single point grounding system. cs (pin 5): active low digital input. a low on this pin enables the sdo digital output and wakes up the adc. following each conversion, the adc automatically enters the sleep mode and remains in this low power state as long as cs is high. a low on cs wakes up the adc. a low-to-high transition on this pin disables the sdo digital output. a low-to-high transition on cs during the data output transfer aborts the data transfer and starts a new conversion. sdo (pin 6): three-state digital output. during the data output period this pin is used for serial data output. when the chip select cs is high (cs = v cc ), the sdo pin is in a high impedance state. during the conversion and sleep periods, this pin can be used as a conversion status out- put. the conversion status can be observed by pulling cs low. sck (pin 7): bidirectional digital clock pin. in internal serial clock operation mode, sck is used as digital output for the internal serial interface clock during the data output period. in external serial clock operation mode, sck is used as digital input for the external serial interface. a weak internal pull-up is automatically activated in internal serial clock operation mode. the serial clock mode is determined by the level applied to sck at power up and the falling edge of cs. f o (pin 8): frequency control pin. digital input that controls the adcs notch frequencies and conversion time. when the f o pin is connected to v cc (f o = v cc ), the converter uses its internal oscillator and the digital filters first null is located at 50hz. when the f o pin is connected to gnd (f o = ov), the converter uses its internal oscillator and the digital filter first null is located at 60hz. when f o is driven by an external clock signal with a frequency f eosc , the converter uses this signal as its clock and the digital filter first null is located at a frequency f eosc /2560. pi n fu n ctio n s uu u output rate (hz) 0 tue resolution (bits) 16 18 20 40 2420 g28 14 12 10 10 20 30 50 60 70 80 90 100 v cc = 5v v ref = 5v f o = external t a = 45 c t a = 25 c t a = 90 c output rate (hz) 0 tue resolution (bits) 16 18 20 40 2420 g29 14 12 10 10 20 30 50 60 70 80 90 100 v cc = 3v v ref = 2.5v f o = external t a = 45 c t a = 25 c t a = 90 c
9 LTC2420 uu w fu ctio al block diagra test circuits autocalibration and control dac decimating fir internal oscillator serial interface adc gnd v cc v in sdo sck v ref cs f o (int/ext) 2420 fd 3.4k sdo 2420 tc01 hi-z to v oh v ol to v oh v oh to hi-z c load = 20pf 3.4k sdo 2420 tc02 hi-z to v ol v oh to v ol v ol to hi-z c load = 20pf v cc
10 LTC2420 applicatio s i for atio wu u u the LTC2420 is pin compatible with the ltc2400. the two devices are designed to allow the user to incorporate either device in the same design with no modifications. while the LTC2420 output word length is 24 bits (as opposed to the 32-bit output of the ltc2400), its output clock timing can be identical to the ltc2400. as shown in figure 1, the LTC2420 data output is concluded on the falling edge of the 24th serial clock (sck). in order to maintain drop-in compatibility with the ltc2400, it is possible to clock the LTC2420 with an additional 8 serial clock pulses. this results in 8 additional output bits which are always logic high. converter operation cycle the LTC2420 is a low power, delta-sigma analog-to- digital converter with an easy to use 3-wire serial interface. its operation is simple and made up of three states. the converter operating cycle begins with the conversion, followed by a low power sleep state and concluded with the data output (see figure 2). the 3-wire interface con- sists of serial data output (sdo), a serial clock (sck) and a chip select (cs). initially, the LTC2420 performs a conversion. once the conversion is complete, the device enters the sleep state. while in this sleep state, power consumption is reduced by an order of magnitude. the part remains in the sleep state as long as cs is logic high. the conversion result is held indefinitely in a static shift register while the converter is in the sleep state. once cs is pulled low, the device begins outputting the conversion result. there is no latency in the conversion result. the data output corresponds to the conversion just performed. this result is shifted out on the serial data out pin (sdo) under the control of the serial clock (sck). data is updated on the falling edge of sck allowing the user to reliably latch data on the rising edge of sck, see figure 4. the data output state is concluded once 24 bits are read out of the adc or when cs is brought high. the device automatically initiates a new conversion cycle and the cycle repeats. through timing control of the cs and sck pins, the LTC2420 offers several flexible modes of operation (internal or external sck and free-running conversion modes). these various modes do not require program ming configuration registers; moreover, they do figure 1. LTC2420 compatible timing with the ltc2400 cs sck sdo conversion sleep 8 8 8 8 (optional) eoc = 1 eoc = 1 last 8 bits always 1 eoc = 0 data out 4 status bits 20 data bits data output 2420 f01 conversion convert sleep data output 2420 f02 0 1 cs and sck figure 2. LTC2420 state transition diagram
11 LTC2420 not disturb the cyclic operation described above. these modes of operation are described in detail in the serial interface timing modes section. conversion clock a major advantage delta-sigma converters offer over conventional type converters is an on-chip digital filter (commonly known as sinc or comb filter). for high resolution, low frequency applications, this filter is typi- cally designed to reject line frequencies of 50hz or 60hz plus their harmonics. in order to reject these frequencies in excess of 110db, a highly accurate conversion clock is required. the LTC2420 incorporates an on-chip highly accurate oscillator. this eliminates the need for external frequency setting components such as crystals or oscilla- tors. clocked by the on-chip oscillator, the LTC2420 rejects line frequencies (50hz or 60hz 2%) a minimum of 110db. ease of use the LTC2420 data output has no latency, filter settling or redundant data associated with the conversion cycle. there is a one-to-one correspondence between the conversion and the output data. therefore, multiplexing an analog input voltage is easy. the LTC2420 performs offset and full-scale calibrations every conversion cycle. this calibration is transparent to the user and has no effect on the cyclic operation de- scribed above. the advantage of continuous calibration is extreme stability of offset and full-scale readings with re- spect to time, supply voltage change and temperature drift. power-up sequence the LTC2420 automatically enters an internal reset state when the power supply voltage v cc drops below approxi- mately 2.2v. this feature guarantees the integrity of the conversion result and of the serial interface mode selec- tion which is performed at the initial power-up. (see the 2-wire i/o sections in the serial interface timing modes section.) when the v cc voltage rises above this critical threshold, the converter creates an internal power-on-reset (por) signal with duration of approximately 0.5ms. the por signal clears all internal registers. following the por signal, the LTC2420 starts a normal conversion cycle and follows the normal succession of states described above. the first conversion result following por is accurate within the specifications of the device. reference voltage range the LTC2420 can accept a reference voltage from 0v to v cc . the converter output noise is determined by the thermal noise of the front-end circuits, and as such, its value in microvolts is nearly constant with reference voltage. a decrease in reference voltage will not signifi- cantly improve the converters effective resolution. on the other hand, a reduced reference voltage will improve the overall converter inl performance. the recommended range for the LTC2420 voltage reference is 100mv to v cc . input voltage range the converter is able to accommodate system level offset and gain errors as well as system level overrange situa- tions due to its extended input range, see figure 3. the LTC2420 converts input signals within the extended input range of C 0.125 ? v ref to 1.125 ? v ref . for large values of v ref , this range is limited by the absolute maximum voltage range of C 0.3v to (v cc + 0.3v). beyond this range, the input esd protection devices begin to turn on and the errors due to the input leakage current increase rapidly. input signals applied to v in may extend below ground by C 300mv and above v cc by 300mv. in order to limit any applicatio s i for atio wu u u 2420 f03 v cc + 0.3v 9/8v ref v ref 1/2v ref 0.3v 1/8v ref 0 normal input range extended input range absolute maximum input range figure 3. LTC2420 input range
12 LTC2420 applicatio s i for atio wu u u fault current, a resistor of up to 25k may be added in series with the v in pin without affecting the performance of the device. in the physical layout, it is important to maintain the parasitic capacitance of the connection between this series resistance and the v in pin as low as possible; therefore, the resistor should be located as close as practical to the v in pin. the effect of the series resistance on the converter accuracy can be evaluated from the curves presented in the analog input/reference current section. in addition, a series resistor will introduce a temperature dependent offset error due to the input leak- age current. a 1na input leakage current will develop a 1ppm offset error on a 5k resistor if v ref = 5v. this error has a very strong temperature dependency. output data format the LTC2420 serial output data stream is 24 bits long. the first 4 bits represent status information indicating the sign, input range and conversion state. the next 20 bits are the conversion result, msb first. bit 23 (first output bit) is the end of conversion (eoc) indicator. this bit is available at the sdo pin during the conversion and sleep states whenever the cs pin is low. this bit is high during the conversion and goes low when the conversion is complete. bit 22 (second output bit) is a dummy bit (dmy) and is always low. bit 21 (third output bit) is the conversion result sign indi- cator (sig). if v in is >0, this bit is high. if v in is <0, this bit is low. the sign bit changes state during the zero code. bit 20 (fourth output bit) is the extended input range (exr) indicator. if the input is within the normal input range 0 v in v ref , this bit is low. if the input is outside the normal input range, v in > v ref or v in < 0, this bit is high. the function of these bits is summarized in table 1. table 1. LTC2420 status bits bit 23 bit 22 bit 21 bit 20 input range eoc dmy sig exr v in > v ref 0 011 0 < v in v ref 0 010 v in = 0 + /0 C 0 0 1/0 0 v in < 0 0 001 bit 19 (fifth output bit) is the most significant bit (msb). bits 19-0 are the 20-bit conversion result msb first. bit 0 is the least significant bit (lsb). data is shifted out of the sdo pin under control of the serial clock (sck), see figure 4. whenever cs is high, sdo remains high impedance and any sck clock pulses are ignored by the internal data out shift register. in order to shift the conversion result out of the device, cs must first be driven low. eoc is seen at the sdo pin of the device once cs is pulled low. eoc changes real time from high to low at the completion of a conversion. this signal may be used as an interrupt for an external micro- controller. bit 23 (eoc) can be captured on the first rising edge of sck. bit 22 is shifted out of the device on the first falling edge of sck. the final data bit (bit 0) is shifted out on the falling edge of the 23rd sck and may be latched on figure 4. output data timing msb ext sig ? 12345 192024 bit 0 bit 19 bit 4 lsb 20 bit 20 bit 21 bit 22 sdo sck cs eoc bit 23 sleep data output conversion 2420 f04 hi-z
13 LTC2420 applicatio s i for atio wu u u table 2. LTC2420 output data format bit 23 bit 22 bit 21 bit 20 bit 19 bit 18 bit 17 bit 16 bit 15 bit 0 input voltage eoc dmy sig exr msb lsb v in > 9/8 ? v ref 0 0 1100 0 11...1 9/8 ? v ref 0 0 1100 0 11...1 v ref + 1lsb 0 0 1100 0 00...0 v ref 0 0 1011 1 11...1 3/4v ref + 1lsb 0 0 1011 0 00...0 3/4v ref 0 0 1010 1 11...1 1/2v ref + 1lsb 0 0 1010 0 00...0 1/2v ref 0 0 1001 1 11...1 1/4v ref + 1lsb 0 0 1001 0 00...0 1/4v ref 0 0 1000 1 11...1 0 + /0 C 0 01/0*000 0 00...0 C1lsb 0 0 0111 1 11...1 C1/8 ? v ref 0 0 0111 1 00...0 v in < C1/8 ? v ref 0 0 0111 1 00...0 *the sign bit changes state during the 0 code. the rising edge of the 24th sck pulse. on the falling edge of the 24th sck pulse, sdo goes high indicating a new conversion cycle has been initiated. this bit serves as eoc (bit 23) for the next conversion cycle. table 2 summarizes the output data format. as long as the voltage on the v in pin is maintained within the C 0.3v to (v cc + 0.3v) absolute maximum operating range, a conversion result is generated for any input value from C 0.125 ? v ref to 1.125 ? v ref . for input voltages greater than 1.125 ? v ref , the conversion result is clamped to the value corresponding to 1.125 ? v ref . for input voltages below C 0.125 ? v ref , the conversion result is clamped to the value corresponding to C 0.125 ? v ref . frequency rejection selection (f o pin connection) the LTC2420 internal oscillator provides better than 110db normal mode rejection at the line frequency and its har- monics for 50hz 2% or 60hz 2%. for 60hz rejection, f o (pin 8) should be connected to gnd (pin 4) while for 50hz rejection the f o pin should be connected to v cc (pin 1). the selection of 50hz or 60hz rejection can also be made by driving f o to an appropriate logic level. a selection change during the sleep or data output states will not disturb the converter operation. if the selection is made during the conversion state, the result of the conversion in progress may be outside specifications but the following conversions will not be affected. when a fundamental rejection frequency different from 50hz or 60hz is required or when the converter must be synchronized with an outside source, the LTC2420 can operate with an external conversion clock. the converter automatically detects the presence of an external clock signal at the f o pin and turns off the internal oscillator. the frequency f eosc of the external signal must be at least 2560hz (1hz notch frequency) to be detected. the exter- nal clock signal duty cycle is not significant as long as the minimum and maximum specifications for the high and low periods t heo and t leo are observed. while operating with an external conversion clock of a frequency f eosc , the LTC2420 provides better than 110db normal mode rejection in a frequency range f eosc /2560 4% and its harmonics. the normal mode rejection as a function of the input frequency deviation from f eosc /2560 is shown in figure 5.
14 LTC2420 applicatio s i for atio wu u u input frequency deviation from notch frequency (%) 128404812 rejection (db) 2420 f05 ?0 ?0 ?0 ?0 100 110 120 130 140 figure 5. LTC2420 normal mode rejection when using an external oscillator of frequency f eosc whenever an external clock is not present at the f o pin, the converter automatically activates its internal oscillator and enters the internal conversion clock mode. the LTC2420 operation will not be disturbed if the change of conversion clock source occurs during the sleep state or during the data output state while the converter uses an external serial clock. if the change occurs during the conversion state, the result of the conversion in progress may be outside specifications but the following conversions will not be affected. if the change occurs during the data output state and the converter is in the internal sck mode, the serial clock duty cycle may be affected but the serial data stream will remain valid. table 3 summarizes the duration of each state as a function of f o . serial interface the LTC2420 transmits the conversion results and re- ceives the start of conversion command through a syn- chronous 3-wire interface. during the conversion and sleep states, this interface can be used to assess the converter status and during the data output state it is used to read the conversion result. serial clock input/output (sck) the serial clock signal present on sck (pin 7) is used to synchronize the data transfer. each bit of data is shifted out the sdo pin on the falling edge of the serial clock. in the internal sck mode of operation, the sck pin is an output and the LTC2420 creates its own serial clock by dividing the internal conversion clock by 8. in the external sck mode of operation, the sck pin is used as input. the internal or external sck mode is selected on power-up and then reselected every time a high-to-low transition is detected at the cs pin. if sck is high or floating at power- up or during this transition, the converter enters the inter- nal sck mode. if sck is low at power-up or during this transition, the converter enters the external sck mode. table 3. LTC2420 state duration state operating mode duration convert internal oscillator f o = low 133ms (60hz rejection) f o = high 160ms (50hz rejection) external oscillator f o = external oscillator 20510/f eosc s with frequency f eosc khz (f eosc /2560 rejection) sleep as long as cs = high until cs = 0 and sck data output internal serial clock f o = low/high as long as cs = low but not longer than 1.26ms (internal oscillator) (24 sck cycles) f o = external oscillator with as long as cs = low but not longer than 256/f eosc ms frequency f eosc khz (24 sck cycles) external serial clock with as long as cs = low but not longer than 24/f sck ms frequency f sck khz (24 sck cycles)
15 LTC2420 applicatio s i for atio wu u u serial data output (sdo) the serial data output pin, sdo (pin 6), drives the serial data during the data output state. in addition, the sdo pin is used as an end of conversion indicator during the conversion and sleep states. when cs (pin 5) is high, the sdo driver is switched to a high impedance state. this allows sharing the serial interface with other devices. if cs is low during the convert or sleep state, sdo will output eoc. if cs is low during the conversion phase, the eoc bit appears high on the sdo pin. once the conversion is complete, eoc goes low. the device remains in the sleep state until the first rising edge of sck occurs while cs is low. chip select input (cs) the active low chip select, cs (pin 5), is used to test the conversion status and to enable the data output transfer as described in the previous sections. in addition, the cs signal can be used to trigger a new conversion cycle before the entire serial data transfer has been completed. the LTC2420 will abort any serial data transfer in progress and start a new conversion cycle any- time a low-to-high transition is detected at the cs pin after the converter has entered the data output state (i.e., after the first rising edge of sck occurs while cs is low). finally, cs can be used to control the free-running modes of operation, see serial interface timing modes section. grounding cs will force the adc to continuously convert at the maximum output rate selected by f o . tying a capacitor to cs will reduce the output rate and power dissipation by a factor proportional to the capacitors value, see figures 13 to 15. serial interface timing modes the LTC2420s 3-wire interface is spi and microwire compatible. this interface offers several flexible modes of operation. these include internal/external serial clock, 2- or 3-wire i/o, single cycle conversion and autostart. the following sections describe each of these serial interface timing modes in detail. in all these cases, the converter can use the internal oscillator (f o = low or f o = high) or an external oscillator connected to the f o pin. refer to table 4 for a summary. external serial clock, single cycle operation (spi/microwire compatible) this timing mode uses an external serial clock to shift out the conversion result and a cs signal to monitor and control the state of the conversion cycle, see figure 6. the serial clock mode is selected on the falling edge of cs. to select the external serial clock mode, the serial clock pin (sck) must be low during each cs falling edge. the serial data output pin (sdo) is hi-z as long as cs is high. at any time during the conversion cycle, cs may be pulled low in order to monitor the state of the converter. while cs is pulled low, eoc is output to the sdo pin. eoc = 1 while a conversion is in progress and eoc = 0 if the device is in the sleep state. independent of cs, the device automatically enters the low power sleep state once the conversion is complete. when the device is in the sleep state (eoc = 0), its conversion result is held in an internal static shift regis- ter. the device remains in the sleep state until the first rising edge of sck is seen while cs is low. data is shifted out the sdo pin on each falling edge of sck. this enables table 4. LTC2420 interface timing modes conversion data connection sck cycle output and configuration source control control waveforms external sck, single cycle conversion external cs and sck cs and sck figures 6, 7 external sck, 2-wire i/o external sck sck figure 8 internal sck, single cycle conversion internal cs cs figures 9, 10 internal sck, 2-wire i/o, continuous conversion internal continuous internal figure 11 internal sck, autostart conversion internal c ext internal figure 12
16 LTC2420 eoc bit 23 sdo sck (external) cs v cc f o v ref sck v in sdo gnd cs v ref 0.1v to v cc v in 0.12v ref to 1.12v ref 1 f 2.7v to 5.5v LTC2420 test eoc msb lsb 20 exr sig bit 0 bit 4 bit 19 bit 18 bit 20 bit 21 bit 22 sleep data output conversion 2420 f06 conversion = 50hz rejection = external oscillator = 60hz rejection hi-z hi-z hi-z v cc test eoc test eoc applicatio s i for atio wu u u figure 6. external serial clock, single cycle operation external circuitry to latch the output on the rising edge of sck. eoc can be latched on the first rising edge of sck and the last bit of the conversion result can be latched on the 24th rising edge of sck. on the 24th falling edge of sck, the device begins a new conversion. sdo goes high (eoc = 1) indicating a conversion is in progress. at the conclusion of the data cycle, cs may remain low and eoc monitored as an end-of-conversion interrupt. alternatively, cs may be driven high setting sdo to hi-z. as described above, cs may be pulled low at any time in order to monitor the conversion status. typically, cs remains low during the data output state. however, the data output state may be aborted by pulling cs high anytime between the first rising edge and the 24th falling edge of sck, see figure 7. on the rising edge of cs, the device aborts the data output state and imme- diately initiates a new conversion. this is useful for sys- tems not requiring all 24 bits of output data, aborting an invalid conversion cycle or synchronizing the start of a conversion. external serial clock, 2-wire i/o this timing mode utilizes a 2-wire serial i/o interface. the conversion result is shifted out of the device by an exter- nally generated serial clock (sck) signal, see figure 8. cs may be permanently tied to ground (pin 4), simplifying the user interface or isolation barrier. the external serial clock mode is selected at the end of the power-on reset (por) cycle. the por cycle is concluded approximately 0.5ms after v cc exceeds 2.2v. the level applied to sck at this time determines if sck is internal or external. sck must be driven low prior to the end of por in order to enter the external serial clock timing mode. since cs is tied low, the end-of-conversion (eoc) can be continuously monitored at the sdo pin during the convert and sleep states. eoc may be used as an interrupt to an external controller indicating the conversion result is ready. eoc = 1 while the conversion is in progress and eoc = 0 once the conversion enters the low power sleep state. on the falling edge of eoc, the conversion result is loaded
17 LTC2420 applicatio s i for atio wu u u v cc f o v ref sck v in sdo gnd cs v ref 0.1v to v cc v in 0.12v ref to 1.12v ref = 50hz rejection = external oscillator = 60hz rejection 1 f 2.7v to 5.5v LTC2420 sdo sck (external) cs data output conversion sleep sleep test eoc test eoc data output hi-z hi-z hi-z conversion 2420 f07 msb exr sig bit 8 bit 19 bit 9 bit 20 bit 21 bit 22 eoc bit 23 bit 0 eoc hi-z v cc test eoc eoc bit 23 sdo sck (external) cs v cc f o v ref sck v in sdo gnd cs v ref 0.1v to v cc v in 0.12v ref to 1.12v ref 1 f 2.7v to 5.5v LTC2420 msb exr sig bit 0 lsb 20 bit 4 bit 19 bit 18 bit 20 bit 21 bit 22 sleep data output conversion 2420 f07 conversion = 50hz rejection = external oscillator = 60hz rejection v cc figure 7. external serial clock, reduced data output length figure 8. external serial clock, cs = 0 operation
18 LTC2420 into an internal static shift register. the device remains in the sleep state until the first rising edge of sck. data is shifted out the sdo pin on each falling edge of sck enabling external circuitry to latch data on the rising edge of sck. eoc can be latched on the first rising edge of sck. on the 24th falling edge of sck, sdo goes high (eoc = 1) indicating a new conversion has begun. internal serial clock, single cycle operation this timing mode uses an internal serial clock to shift out the conversion result and a cs signal to monitor and control the state of the conversion cycle, see figure 9. in order to select the internal serial clock timing mode, the serial clock pin (sck) must be floating (hi-z) or pulled high prior to the falling edge of cs. the device will not enter the internal serial clock mode if sck is driven low on the falling edge of cs. an internal weak pull-up resistor is active on the sck pin during the falling edge of cs; therefore, the internal serial clock timing mode is auto- matically selected if sck is not externally driven. the serial data output pin (sdo) is hi-z as long as cs is high. at any time during the conversion cycle, cs may be pulled low in order to monitor the state of the converter. once cs is pulled low, sck goes low and eoc is output to the sdo pin. eoc = 1 while a conversion is in progress and eoc = 0 if the device is in the sleep state. when testing eoc, if the conversion is complete (eoc = 0), the device will exit the sleep state and enter the data output state if cs remains low. in order to prevent the device from exiting the low power sleep state, cs must be pulled high before the first rising edge of sck. in the internal sck timing mode, sck goes high and the device begins outputting data at time t eoctest after the falling edge of cs (if eoc = 0) or t eoctest after eoc goes low (if cs is low during the falling edge of eoc). the value of t eoctest is 23 m s if the device is using its internal oscillator (f 0 = logic low or high). if f o is driven by an external oscillator of frequency f eosc , then t eoctest is 3.6/f eosc . if cs is pulled high before time t eoctest , the device remains in the sleep state. the conversion result is held in the internal static shift register. if cs remains low longer than t eoctest , the first rising edge of sck will occur and the conversion result is serially shifted out of the sdo pin. the data output cycle begins on this first rising edge of sck and concludes after the 24th rising edge. data is shifted out the sdo pin on each falling edge of sck. the internally generated serial clock is output to the sck pin. this signal may be used to shift the sdo sck (internal) cs msb exr sig bit 0 lsb 20 bit 4 test eoc bit 19 bit 18 bit 20 bit 21 bit 22 eoc bit 23 sleep data output conversion conversion 2420 f09 LTC2420 v cc 10k = 50hz rejection = external oscillator = 60hz rejection hi-z hi-z hi-z hi-z v cc test eoc figure 9. internal serial clock, single cycle operation applicatio s i for atio wu u u
19 LTC2420 conversion result into external circuitry. eoc can be latched on the first rising edge of sck and the last bit of the conversion result on the 24th rising edge of sck. after the 24th rising edge, sdo goes high (eoc = 1), sck stays high, and a new conversion starts. typically, cs remains low during the data output state. however, the data output state may be aborted by pulling cs high anytime between the first and 24th rising edge of sck, see figure 10. on the rising edge of cs, the device aborts the data output state and immediately initiates a new conversion. this is useful for systems not requiring all 24 bits of output data, aborting an invalid conversion cycle, or synchronizing the start of a conversion. if cs is pulled high while the converter is driving sck low, the internal pull-up is not available to restore sck to a logic high state. this will cause the device to exit the internal serial clock mode on the next falling edge of cs. this can be avoided by adding an external 10k pull-up resistor to the sck pin or by never pulling cs high when sck is low. whenever sck is low, the LTC2420s internal pull-up at pin sck is disabled. normally, sck is not externally driven if the device is in the internal sck timing mode. however, certain applications may require an external driver on sck. if this driver goes hi-z after outputting a low signal, the LTC2420s internal pull-up remains disabled. hence, sck remains low. on the next falling edge of cs, the device is switched to the external sck timing mode. by adding an external 10k pull-up resistor to sck, this pin goes high once the external driver goes hi-z. on the next cs falling edge, the device will remain in the internal sck timing mode. a similar situation may occur during the sleep state when cs is pulsed high-low-high in order to test the conver- sion status. if the device is in the sleep state (eoc = 0), sck will go low. once cs goes high (within the time period defined above as t eoctest ), the internal pull-up is activated. for a heavy capacitive load on the sck pin, the internal pull-up may not be adequate to return sck to a high level before cs goes low again. this is not a concern under normal conditions where cs remains low after detecting eoc = 0. this situation is easily overcome by adding an external 10k pull-up resistor to the sck pin. applicatio s i for atio wu u u sdo sck (internal) cs >t eoctest msb exr sig bit 8 test eoc test eoc bit 19 bit 18 bit 20 bit 21 bit 22 eoc bit 23 eoc bit 0 sleep data output hi-z hi-z hi-z hi-z hi-z data output conversion conversion sleep 2420 f10 LTC2420 v cc 10k = 50hz rejection = external oscillator = 60hz rejection v cc test eoc figure 10. internal serial clock, reduced data output length
20 LTC2420 internal serial clock, 2-wire i/o, continuous conversion this timing mode uses a 2-wire, all output (sck and sdo) interface. the conversion result is shifted out of the device by an internally generated serial clock (sck) signal, see figure 11. cs may be permanently tied to ground (pin 4), simplifying the user interface or isolation barrier. the internal serial clock mode is selected at the end of the power-on reset (por) cycle. the por cycle is concluded approximately 0.5ms after v cc exceeds 2.2v. an internal weak pull-up is active during the por cycle; therefore, the internal serial clock timing mode is automatically selected if sck is not externally driven low (if sck is loaded such that the internal pull-up cannot pull the pin high, the external sck mode will be selected). during the conversion, the sck and the serial data output pin (sdo) are high (eoc = 1). once the conversion is complete, sck and sdo go low (eoc = 0) indicating the conversion has finished and the device has entered the low power sleep state. the part remains in the sleep state a minimum amount of time (1/2 the internal sck period) applicatio s i for atio wu u u then immediately begins outputting data. the data output cycle begins on the first rising edge of sck and ends after the 24th rising edge. data is shifted out the sdo pin on each falling edge of sck. the internally generated serial clock is output to the sck pin. this signal may be used to shift the conversion result into external circuitry. eoc can be latched on the first rising edge of sck and the last bit of the conversion result can be latched on the 24th rising edge of sck. after the 24th rising edge, sdo goes high (eoc = 1) indicating a new conversion is in progress. sck remains high during the conversion. internal serial clock, autostart conversion this timing mode is identical to the internal serial clock, 2-wire i/o described above with one additional feature. instead of grounding cs, an external timing capacitor is tied to cs. while the conversion is in progress, the cs pin is held high by an internal weak pull-up. once the conversion is complete, the device enters the low power sleep state and an internal 25na current source begins discharging the sdo sck (internal) cs lsb 20 msb exr sig bit 4 bit 0 bit 19 bit 18 bit 20 bit 21 bit 22 eoc bit 23 sleep data output conversion conversion 2420 f11 v cc f o v ref sck v in sdo gnd cs v ref 0.1v to v cc v in 0.12v ref to 1.12v ref 1 f 2.7v to 5.5v LTC2420 = 50hz rejection = external oscillator = 60hz rejection v cc figure 11. internal serial clock, continuous operation
21 LTC2420 applicatio s i for atio wu u u capacitor tied to cs, see figure 12. the time the converter spends in the sleep state is determined by the value of the external timing capacitor, see figures 13 and 14. once the voltage at cs falls below an internal threshold ( ? 1.4v), the device automatically begins outputting data. the data output cycle begins on the first rising edge of sck and ends on the 24th rising edge. data is shifted out the sdo pin on each falling edge of sck. the internally generated serial clock is output to the sck pin. this signal may be used to shift the conversion result into external circuitry. after the 24th rising edge, cs is pulled high and a new conversion is immediately started. this is useful in appli- cations requiring periodic monitoring and ultralow power. figure 15 shows the average supply current as a function of capacitance on cs. it should be noticed that the external capacitor discharge current is kept very small in order to decrease the con- verter power dissipation in the sleep state. in the autostart mode the analog voltage on the cs pin cannot be observed without disturbing the converter operation using a regular oscilloscope probe. when using this configuration, it is important to minimize the external leakage current at the cs pin by using a low leakage external capacitor and properly cleaning the pcb surface. sdo hi-z hi-z sck (internal) cs v cc gnd 2420 f12 v cc f o v ref sck v in sdo gnd c ext cs v ref 0.1v to v cc v in 0.12v ref to 1.12v ref 1 f 2.7v to 5.5v LTC2420 bit 0 sig bit 21 bit 22 sleep data output conversion conversion eoc bit 23 = 50hz rejection = external oscillator = 60hz rejection v cc figure 12. internal serial clock, autostart operation capacitance on cs (pf) 1 5 6 7 1000 10000 2420 f13 4 3 10 100 100000 2 1 0 t sample (sec) v cc = 5v v cc = 3v figure 13. cs capacitance vs f sample
22 LTC2420 applicatio s i for atio wu u u the internal serial clock mode is selected every time the voltage on the cs pin crosses an internal threshold volt- age. an internal weak pull-up at the sck pin is active while cs is discharging; therefore, the internal serial clock timing mode is automatically selected if sck is floating. it is important to ensure there are no external drivers pulling sck low while cs is discharging. digital signal levels the LTC2420s digital interface is easy to use. its digital inputs (f o , cs and sck in external sck mode of operation) accept standard ttl/cmos logic levels and the internal hysteresis receivers can tolerate edge rates as slow as 100 m s. however, some considerations are required to take advantage of exceptional accuracy and low supply current. capacitance on cs (pf) 0 sample rate (hz) 3 4 5 1000 100000 2420 f14 2 1 0 10 100 10000 6 7 8 v cc = 5v v cc = 3v figure 14. cs capacitance vs output rate capacitance on cs (pf) 1 0 supply current ( a rms ) 50 100 150 200 250 300 10 100 1000 10000 2420 f15 100000 v cc = 5v v cc = 3v figure 15. cs capacitance vs supply current the digital output signals (sdo and sck in internal sck mode of operation) are less of a concern because they are not generally active during the conversion state. in order to preserve the LTC2420s accuracy, it is very important to minimize the ground path impedance which may appear in series with the input and/or reference signal and to reduce the current which may flow through this path. the gnd pin should be connected to a low resistance ground plane through a minimum length trace. the use of multiple via holes is recommended to further reduce the connection resistance. the LTC2420s power supply cur- rent flowing through the 0.01 w resistance of the common ground pin will develop a 2.5 m v offset signal. for a refer- ence voltage v ref = 2.5v, this represents a 1ppm offset error. in an alternative configuration, the gnd pin of the converter can be the single-point-ground in a single point grounding system. the input signal ground, the reference signal ground, the digital drivers ground (usually the digital ground) and the power supply ground (the analog ground) should be connected in a star configuration with the com- mon point located as close to the gnd pin as possible. the power supply current during the conversion state should be kept to a minimum. this is achieved by restrict- ing the number of digital signal transitions occurring during this period. while a digital input signal is in the range 0.5v to (v cc C 0.5v), the cmos input receiver draws additional current from the power supply. it should be noted that, when any one of the digital input signals (f o , cs and sck in external sck mode of operation) is within this range, the LTC2420 power supply current may increase even if the signal in question is at a valid logic level. for micropower operation and in order to minimize the potential errors due to additional ground pin current, it is recommended to drive all digital input signals to full cmos levels [v il < 0.4v and v oh > (v cc C 0.4v)]. severe ground pin current disturbances can also occur due to the undershoot of fast digital input signals. under- shoot and overshoot can occur because of the imped- ance mismatch at the converter pin when the transition time of an external control signal is less than twice the
23 LTC2420 propagation delay from the driver to LTC2420. for refer- ence, on a regular fr-4 board, signal propagation veloc- ity is approximately 183ps/inch for internal traces and 170ps/inch for surface traces. thus, a driver generating a control signal with a minimum transition time of 1ns must be connected to the converter pin through a trace shorter than 2.5 inches. this problem becomes particu- larly difficult when shared control lines are used and multiple reflections may occur. the solution is to care- fully terminate all transmission lines close to their char- acteristic impedance. parallel termination near the LTC2420 pin will eliminate this problem but will increase the driver power dissipation. a series resistor between 27 w and 56 w placed near the driver or near the LTC2420 pin will also eliminate this problem without additional power dissipation. the actual resistor value depends upon the trace impedance and connection topology. driving the input and reference the analog input and reference of the typical delta-sigma analog-to-digital converter are applied to a switched ca- pacitor network. this network consists of capacitors switch- ing between the analog input (v in ), ground (pin 4) and the reference (v ref ). the result is small current spikes seen at both v in and v ref . a simplified input equivalent circuit is shown in figure 16. the key to understanding the effects of this dynamic input current is based on a simple first order rc time constant model. using the internal oscillator, the LTC2420s inter- nal switched capacitor network is clocked at 153,600hz corresponding to a 6.5 m s sampling period. fourteen time constants are required each time a capacitor is switched in order to achieve 1ppm settling accuracy. therefore, the equivalent time constant at v in and v ref should be less than 6.5 m s/14 = 460ns in order to achieve 1ppm accuracy. input current (v in ) if complete settling occurs on the input, conversion re- sults will be uneffected by the dynamic input current. if the settling is incomplete, it does not degrade the linearity performance of the device. it simply results in an offset/ full-scale shift, see figure 17. to simplify the analysis of input dynamic current, two separate cases are assumed: large capacitance at v in (c in > 0.01 m f) and small capaci- tance at v in (c in < 0.01 m f). if the total capacitance at v in (see figure 18) is small (< 0.01 m f), relatively large external source resistances (up to 80k for 20pf parasitic capacitance) can be tolerated without any offset/full-scale error. figures 19 and 20 show a family of offset and full-scale error curves for various small valued input capacitors (c in < 0.01 m f) as a function of input source resistance. applicatio s i for atio wu u u v ref v in v cc r sw 5k average input current: i in = 0.25(v in ?0.5 ?v ref )fc eq i ref(leak) i ref(leak) v cc r sw 5k c eq 1pf (typ) r sw 5k i in(leak) i in 2420 f16 i in(leak) switching frequency f = 153.6khz for internal oscillator (f o = logic low or high) f = f eosc for external oscillators gnd figure 16. LTC2420 equivalent analog input circuit 0 tue v ref /2 v in 2420 f17 v ref c in 2420 f18 intput signal source r source v in LTC2420 c par @ 20pf figure 17. offset/full-scale shift figure 18. an rc network at v in
24 LTC2420 applicatio s i for atio wu u u for large input capacitor values (c in > 0.01 m f), the input spikes are averaged by the capacitor into a dc current. the gain shift becomes a linear function of input source resistance independent of input capacitance, see figures 21 and 22. the equivalent input impedance is 16.6m w . this results in 150na of input dynamic current at the extreme values of v in (v in = 0v and v in = v ref , when v ref = 5v). this corresponds to a 0.3ppm shift in offset and full-scale readings for every 10 w of input source resistance. in addition to the input current spikes, the input esd protection diodes have a temperature dependent leakage current. this leakage current, nominally 1na ( 10na max), results in a fixed offset shift of 10 m v for a 10k source resistance. r source ( ) 1 offset error (ppm) 30 40 50 10k 2420 f19 20 10 0 10 100 1k 100k v cc = 5v v ref = 5v v in = 0v t a = 25 c c in = 100pf c in = 1000pf c in = 0pf c in = 0.01 f figure 19. offset vs r source (small c) figure 20. full-scale error vs r source (small c) reference current (v ref ) similar to the analog input, the reference input has a dynamic input current. this current has negligible effect on the offset. however, the reference current at v in = v ref is similar to the input current at full-scale. for large values of reference capacitance (c vref > 0.01 m f), the full-scale error shift is 0.03ppm/ w of external reference resistance independent of the capacitance at v ref , see figure 23. if the capacitance tied to v ref is small (c vref < 0.01 m f), an input resistance of up to 80k (20pf parasitic capacitance at v ref ) may be tolerated, see figure 24. unlike the analog input, the integral nonlinearity of the device can be degraded with excessive external rc time constants tied to the reference input. if the capacitance at r source ( ) 0 25 30 35 600 800 2420 f21 20 15 200 400 1000 10 5 0 offset error (ppm) c in = 22 f c in = 10 f c in = 1 f c in = 0.1 f c in = 0.01 f c in = 0.001 f v cc = 5v v ref = 5v v in = 0v t a = 25 c r source ( ) 0 full-scale error (ppm) ?0 ?5 ?0 600 1000 2420 f22 ?5 ?0 ?5 200 400 800 ? 0 5 c in = 22 f c in = 10 f c in = 1 f c in = 0.1 f c in = 0.01 f c in = 0.001 f v cc = 5v v ref = 5v v in = 0v t a = 25 c figure 21. offset vs r source (large c) figure 22. full-scale error vs r source (large c) r source ( ) 1 ?0 full-scale error (ppm) ?0 ?0 ?0 ?0 0 10 10 100 1k 10k 2420 f20 100k v cc = 5v v ref = 5v v in = 5v t a = 25 c c in = 0.01 f c in = 100pf c in = 1000pf c in = 0pf
25 LTC2420 applicatio s i for atio wu u u node v ref is small (c vref < 0.01 m f), the reference input can tolerate large external resistances without reduction in inl, see figure 25. if the external capacitance is large (c vref > 0.01 m f), the linearity will be degraded by 0.015ppm/ w independent of capacitance at v ref , see figure 26. in addition to the dynamic reference current, the v ref esd protection diodes have a temperature dependent leakage current. this leakage current, nominally 1na ( 10na max), results in a fixed full-scale shift of 10 m v for a 10k source resistance. antialiasing one of the advantages delta-sigma adcs offer over con- ventional adcs is on-chip digital filtering. combined with a large oversampling ratio, the LTC2420 significantly simplifies antialiasing filter requirements. the digital filter provides very high rejection except at integer multiples of the modulator sampling frequency (f s ), see figure 27. the modulator sampling frequency is 256 ? f o , where f o is the notch frequency (typically 50hz or 60hz). the bandwidth of signals not rejected by the digital filter is narrow ( ? 0.2%) compared to the bandwidth of the frequencies rejected. resistance at v ref ( ) 0 40 50 60 600 800 2420 f23 30 20 200 400 1000 10 0 ?0 full-scale error (ppm) c vref = 22 f c vref = 10 f c vref = 1 f c vref = 0.1 f c vref = 0.01 f c vref = 0.001 f v cc = 5v v ref = 5v v in = 5v t a = 25 c resistance at v ref ( ) 1 300 400 500 1k 10k 2420 f24 200 100 10 100 100k 0 100 200 voltage v cc = 5v v ref = 5v v in = 5v t a = 25 c c vref = 0.01 f c vref = 100pf c vref = 1000pf c vref = 0pf resistance at v ref ( ) 1 30 40 50 1k 10k 2420 f25 20 10 10 100 100k 0 ?0 ?0 inl error (ppm) v cc = 5v v ref = 5v t a = 25 c c vref = 0.01 f c vref = 1000pf c vref = 0pf c vref = 100pf resistance at v ref ( ) 0 6 8 10 600 800 2420 f26 4 2 ? ? ? ? ?0 200 400 1000 0 inl error (ppm) c vref = 22 f c vref = 10 f c vref = 1 f c vref = 0.1 f c vref = 0.01 f c vref = 0.001 f v cc = 5v v ref = 5v t a = 25 c figure 23. full-scale error vs r vref (large c) figure 24. full-scale error vs r vref (small c) figure 25. inl error vs r vref (small c) figure 26. inl error vs r vref (large c)
26 LTC2420 applicatio s i for atio wu u u as a result of the oversampling ratio (256) and the digital filter, minimal (if any) antialias filtering is required in front of the LTC2420. if passive rc components are placed in front of the LTC2420 the input dynamic current should be considered (see input current section). in cases where large effective rc time constants are used, an external buffer amplifier may be required to minimize the effects of input dynamic current. the modulator contained within the LTC2420 can handle large-signal level perturbations without saturating. signal levels up to 40% of v ref do not saturate the analog modu- lator. these signals are limited by the input esd protection to 300mv below ground and 300mv above v cc . operation at higher data output rates the LTC2420 typically operates with an internal oscillator of 153.6khz. this corresponds to a notch frequency of 60hz and an output rate of 7.5 samples/second. the internal oscillator is enabled if the f o pin is logic low (logic high for a 50hz notch). it is possible to drive the f o pin with an external oscillator for higher data output rates. as shown in figure 28, an external clock of 2.048mhz applied to the f o pin results in a notch frequency of 800hz with a data output rate of 100 samples/second. figure 29 shows the total unadjusted error (offset error + full-scale error + inl + dnl) as a function of the output data rate with a 5v reference. the relationship between the output data rate (odr) and the frequency applied to the f o pin (f o ) is: odr = f o /20480 for output data rates up to 50 samples/second, the total unadjusted error (tue) is better than 16 bits, and better than 12 bits at 100 samples/second. as shown in figure 30, for output data rates of 100 samples/second, the tue is better than 15 bits for v ref below 2.5v. figure 31 shows an unaveraged total unadjusted error for the LTC2420 op- erating at 100 samples/second with v ref = 2.5v. figure 32 shows the same device operating with a 5v reference and an output data rate of 7.5 samples/second. at 100 samples/second, the LTC2420 can be used to capture transient data. this is useful for monitoring set- tling or auto gain ranging in a system. the LTC2420 can monitor signals at an output rate of 100 samples/second. input frequency 0 ?0 ?0 0 2420 f27 ?0 100 f s /2 f s 120 140 ?0 rejection (db) figure 27. sinc 4 filter rejection f o sck sdo cs v cc v ref v in gnd 8 7 6 5 1 2 3 4 LTC2420 800hz notch (100 samples/second) 60hz notch (7.5 samples/second) external 2.048mhz clock source internal 153.6khz oscillator 2420 f28 figure 28. selectable 100 samples/second turbo mode output rate (samples/sec) 0 total unadjusted error (ppm) 96 128 160 12 bits 13 bits 14 bits 16 bits 2420 f29 64 32 0 50 100 192 224 256 v ref = 5v 150 figure 29. total error vs output rate (v ref = 5v)
27 LTC2420 figure 31. total unadjusted error at 100 samples/second (no averaging) figure 32. total unadjusted error at 7.5 samples/second (no averaging) figure 30. total error vs v ref (output rate = 100sps) applicatio s i for atio wu u u reference voltage (v) 1.0 total unadjusted error (ppm) 128 192 5.0 2420 f30 64 0 2.0 3.0 4.0 1.5 2.5 3.5 4.5 256 96 160 32 224 output rate = 100sps 12 bits 13 bits 14 bits 15 bits input voltage (v) 0 ?0 total unadjusted error (ppm) ?0 ?5 ?0 ?5 ?0 ? 2420 f31 0 5 10 ?5 2.5 v cc = 5v v ref = 2.5v input voltage (v) 0 total unadjusted error (ppm) ? 0 2 5 2420 f32 ? ? ?0 ? 6 4 v cc = 5v v ref = 5v after acquiring 100 samples/second data the f o pin may be driven low enabling 60hz rejection to 110db and the highest possible dc accuracy. the no latency architecture of the LTC2420 allows consecutive readings (one at 100 samples/second the next at 7.5 samples/second) without interaction between the two readings. as shown in figure 33, the LTC2420 can capture transient data with 90db of dynamic range (with a 300mv p-p input signal at 2hz). the exceptional dc performance of the LTC2420 enables signals to be digitized independent of a large dc offset. figures 34a and 34b show the dynamic performance with a 15hz signal superimposed on a 2v dc level. the same signal with no dc level is shown in figures 34c and 34d.
28 LTC2420 33a. digitized waveform 33b. output fft figure 33. transient signal acquisiton 34a. digitized waveform with 2v dc offset 34b. fft waveform with 2v dc offset 34c. digitized waveform with no offset figure 34. using the LTC2420s high accuracy wide dynamic range to digitize a 300mv p-p 15hz waveform with a large dc offset (v cc = 5v, v ref = 5v) 34d. fft waveform with no offset applicatio s i for atio wu u u time adc output (normalized to volts) 0 0.05 0.10 0.05 0.10 0.20 0.15 0.20 500ms 0.15 f in = 2hz 2420 f33a frequency (hz) magnitude (db) ?0 ?0 ?0 0 ?0 100 120 2hz 100sps 0v offset 2420 f33b time adc output (normalized to volts) 2.00 2.05 2.10 2420 f34a 1.95 1.90 1.80 1.85 2.20 2.15 v in = 300mv p-p + 2v dc frequency (hz) magnitude (db) ?0 ?0 ?0 0 2420 f34b ?0 100 120 15hz 100sps 2v offset time adc output (normalized to volts) 0.00 0.05 0.10 2420 f34c 0.05 0.10 0.20 0.15 0.20 0.15 v in = 300mv p-p + 0v dc frequency (hz) magnitude (db) ?0 ?0 ?0 0 2420 f34d ?0 100 120 15hz 100sps 0v offset
29 LTC2420 synchronization of multiple LTC2420s since the LTC2420s absolute accuracy (total unadjusted error) is 10ppm, applications utilizing multiple matched adcs are possible. simultaneous sampling with two LTC2420s one such application is synchronizing multiple LTC2420s, see figure 35. the start of conversion is synchronized to the rising edge of cs. in order to synchronize multiple LTC2420s, cs is a common input to all the adcs. to prevent the converters from autostarting a new con- version at the end of data output read, 23 or fewer sck clock signals are applied to the LTC2420 instead of 24 (the 24th falling edge would start a conversion). the exact timing and frequency for the sck signal is not critical since it is only shifting out the data. in this case, two LTC2420s simultaneously start and end their conversion cycles under the external control of cs. typical applicatio s u increasing the output rate using multiple LTC2420s a second application uses multiple LTC2420s to increase the effective output rate by 4 , see figure 36. in this case, four LTC2420s are interleaved under the control of sepa- rate cs signals. this increases the effective output rate from 7.5hz to 30hz (up to a maximum of 400hz). addi- tionally, the one-shot output spectrum is unfolded allow- ing further digital signal processing of the conversion results. sck and sdo may be common to all four LTC2420s. the four cs rising edges equally divide one LTC2420 conversion cycle (7.5hz for 60hz notch frequency). in order to synchronize the start of conversion to cs, 23 or less sck clock pulses must be applied to each adc. both the synchronous and 4 output rate applications use the external serial clock and single cycle operation with reduced data output length (see serial interface timing modes section and figure 7). an external oscillator clock is applied commonly to the f o pin of each LTC2420 in order to synchronize the sampling times. both circuits may be extended to include more LTC2420s. 23 or less clock cycles cs sck1 sck2 2420 f35 sdo1 sdo2 23 or less clock cycles LTC2420 #1 v cc v ref v in gnd f o sck sdo cs sck2 sck1 cs sdo1 sdo2 LTC2420 #2 v cc v ref v in gnd f o sck sdo cs controller external oscillator (153,600hz) v ref (0.1v to v cc ) figure 35. synchronous conversionextendable
30 LTC2420 typical applicatio s u cs1 cs2 cs3 2420 f36 cs4 sck 23 or less clock pulses sdo LTC2420 #1 v cc v ref v in gnd f o sck sdo cs sck sdo cs1 cs2 cs3 cs4 LTC2420 #2 v cc v ref v in gnd f o sck sdo cs LTC2420 #3 v cc v ref v in gnd f o sck sdo cs LTC2420 #4 v cc v ref v in gnd f o sck sdo cs controller external oscillator (153,600hz) v ref (0.1v to v cc ) figure 36. 4 output rate LTC2420 system
31 LTC2420 typical applicatio s u single-chip instrumentation amplifier for the LTC2420 the circuit in figure 37 is a simple solution for processing differential signals in pressure transducer, weigh scale or strain gauge applications that can operate on a supply voltage range of 5v to 15v. the circuit uses an lt ? 1920 single-chip instrumentation amplifier to perform a differ- ential to single-ended conversion. the amplifiers output voltage is applied to the LTC2420s input and converted to a digital value with an overall accuracy exceeding 17 bits (0.0008%). key circuit performance results are shown in table 5. the practical gain range for this topology as shown is from 5 to 100 because the LTC2420s wide dynamic range makes gains below 5 virtually unnecessary, whereas gains up to 100 significantly reduce the input referred noise. the optional passive rc lowpass filter between the amplifiers output and the LTC2420s input attenuates high frequency noise and its effects. typically, the filter reduces the magnitude of averaged noise by 30% and improves resolution by 0.5 bit without compromising linearity. resistor r2 performs two functions: it isolates c1 from the LTC2420s input and limits the LTC2420s input current should its input voltage drop below C300mv or swing above v cc + 300mv. the lt1920 is the choice for applications where low cost is important. for applications where more precision is required, the lt1167 is a pin-to-pin alternative choice with a lower offset voltage, lower input bias current and higher gain accuracy than the lt1920. the lt1920s maximum total input-referred offset (v ost ) is 135 m v for a gain of 100. at the same gain, the lt1167s v ost is 63 m v. at gains of 10 or 100, the lt1920s maximum gain error is 0.3% and its maximum gain nonlinearity is 30ppm. at the same gains, the lt1167s maximum gain error is 0.1% and its maximum gain nonlinearity is 15ppm. table 6 summa- rizes the performance of figure 37s circuit using the lt1167. figure 37. the lt1920 is a simple solution that converts a differential input to a ground referred single-ended signal for the LTC2420 v s + v s 7 2 1 8 3 4 6 v in + v in r g r g ** differential input r g 3 2 1 ?? *optional?ee text **r g = 49.4k/(a v ?1): use 5.49k for a v = 10; 499 for a v = 100 ? use short lead lengths ? 48 2420 f37 5 6 7 chip select serial data out serial clock cs sdo sck 0.1 f 0.1 f 5v r1* 47 c1* 1 f single point ?tar?ground r2* 10k 0.1 f v in v ref v refin v cc gnd LTC2420 f o lt1920
32 LTC2420 table 6. typical performance of the LTC2420 adc when used with the lt1167 instrumentation amplifiers in figure 34s differential digitizing circuit v s = 5v v s = 15v parameter a v = 10 a v = 100 a v = 10 a v = 100 total (units) differential input voltage range C 30 to 400 C 3 to 40 C 30 to 500 C 3 to 50 mv zero error C94 C 1590 C 110 C 1470 m v maximum input current 0.5 na nonlinearity 4.1 4.4 4.1 3.7 ppm noise (without averaging) 1.4* 0.19* 1.5* 0.18* m v rms noise (averaged 64 readings) 0.18* 0.02* 0.19* 0.02* m v rms resolution (with averaged readings) 21.4 21.0 21.3 21.1 bits overall accuracy (uncalibrated) 18.2 18.1 18.2 19.4 bits common mode rejection ratio 3 120 db common mode range 2/C1.5** 2.2/C1.7** 11.5/C11** 11.7/C11.2** v *input referred noise for the respective gain. **typical values based on single lab tested sample of each amplifier. typical applicatio s u table 5. typical performance of the LTC2420 adc when used with the lt1920 instrumentation amplifiers in figure 34s differential digitizing circuit v s = 5v v s = 15v parameter a v = 10 a v = 100 a v = 10 a v = 100 total (units) differential input voltage range C 30 to 400 C 3 to 40 C 30 to 500 C 3 to 50 mv zero error C160 C 2650 C 213 C 2625 m v maximum input current 2.0 na nonlinearity 8.2 7.4 6.5 6.1 ppm noise (without averaging) 1.8* 0.25* 1.5* 0.27* m v rms noise (averaged 64 readings) 0.2* 0.03* 0.19* 0.03* m v rms resolution (with averaged readings) 21 20.6 21.3 20.5 bits overall accuracy (uncalibrated) 17.2 17.3 17.5 18.2 bits common mode rejection ratio 3 120 db common mode range 2/C1.5** 2.2/C1.7** 11.5/C11** 11.7/C11.2** v *input referred noise for the respective gain. **typical values based on single lab tested sample of each amplifier.
33 LTC2420 typical applicatio s u using a low power precision reference the circuit in figure 38 shows the connections and by- passing for an lt1461-2.5 as a 2.5v reference. the lt1461 is a bandgap reference capable of 3ppm/ c tem- perature stability yet consumes only 45 m a of current. the 1k resistor between the reference and the adc reduces the transient load changes associated with sampling and produces optimal results. this reference will not impact the noise level of the LTC2420 if signals are less than 60% full scale, and only marginally increases noise approach- ing full scale. even lower power references can be used if only the lower end of the LTC2420 input range is required. a differential to single-ended analog front end figure 39 shows the lt1167 as a means of sensing differential signals. the noise performance of the lt1167 is such that for gains less than 200, the noise floor of the LTC2420 remains the dominant noise source. at the point where the noise of the amplifier begins to dominate, the input referred noise is essentially that of the instrumenta- tion amplifier. the linearity of the instrumentation ampli- fier does, however, degrade at higher gains. as a result, if the full linearity of the LTC2420 is desired, gain in the instrumentation amplifier should be limited to less than 100, possibly requiring averaging multiple samples to extend the resolution below the noise floor. the noise level of the lt1167 at gains greater than 100 is on the order of 50nv rms , although, 1/f noise and temperature effects may degrade this below 0.1hz. the introduction of a filter between the amplifier and the LTC2420 may improve noise levels under some circumstances by reducing noise bandwidth. note that temperature offset drift effects enve- lope detection in the input of the lt1167 if exposed to rfi, thermocouple voltages in connectors, resistors and sol- dered junctions can all compromise results, appearing as drift or noise. turbulent airflow over this circuitry should be avoided. + lt1461-2.5 gnd in 2420 f38 10 f 16v tant to LTC2420 ref out 5v 1k 0.1 f cer + + lt1167 3.5k 4 1 2 r g 5v 8 3 5 1 f 22 5k 1 10 f 2 3 a v = recommended r g : 500 , 0.1% 5ppm/ c + 1 49.4k r g 4 optional 6 2428 f39 ?v 5v LTC2420 figure 38. low power reference figure 39. a differential to single-ended analog front end
34 LTC2420 typical applicatio s u u1-a u1-b u1-c u1-f u1-e to LTC2420 f o pin u1-d 12 5pf 5k 1k 2n3904 10k 47k 1k 47k 10pf 100smps, f o = 2.048mhz 30smps, f o = 614.4khz u1: 74hc14 or equivalent 270pf 34 5 6 12 13 halt 11 10 9 8 2420 f40 figure 40. 2.048mhz oscillator for 100sps output rate 2.048mhz oscillator for 100sps output ratio the oscillator circuit shown in figure 40 can be used to drive the f o pin, boosting the conversion rate of the LTC2420 for applications that do not require a notch at 50hz or 60hz. this oscillator is not sensitive to hysteresis voltage of a schmitt trigger device as are simpler relaxation oscillators using the 74hc14 or similar de- vices. the circuit can be tuned over a 3:1 range with only one resistor and can be gated. the use of transmission gates could be used to shift the frequency in order to provide setable conversion rates.
35 LTC2420 package i for atio u u w dimensions in inches (millimeters) unless otherwise noted. s8 package 8-lead plastic small outline (narrow 0.150) (ltc dwg # 05-08-1610) 0.016 ?0.050 (0.406 ?1.270) 0.010 ?0.020 (0.254 ?0.508) 45 0 ?8 typ 0.008 ?0.010 (0.203 ?0.254) so8 1298 0.053 ?0.069 (1.346 ?1.752) 0.014 ?0.019 (0.355 ?0.483) typ 0.004 ?0.010 (0.101 ?0.254) 0.050 (1.270) bsc 1 2 3 4 0.150 ?0.157** (3.810 ?3.988) 8 7 6 5 0.189 ?0.197* (4.801 ?5.004) 0.228 ?0.244 (5.791 ?6.197) dimension does not include mold flash. mold flash shall not exceed 0.006" (0.152mm) per side dimension does not include interlead flash. interlead flash shall not exceed 0.010" (0.254mm) per side * ** information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no represen- tation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
36 LTC2420 related parts part number description comments lt1019 precision bandgap voltage reference, 2.5v, 5v 3ppm/ c drift, 0.05% max lt1025 micropower thermocouple cold junction compensator 0.5 c initial accuracy, 80 m a supply current ltc1043 dual precision instrumentation switched capacitor precise charge, balanced switching, low power building block ltc1050 precision chopper stabilized op amp no external components 5 m v offset, 1.6 m v p-p noise lt1236a-5 precision bandgap voltage reference, 5v 0.05% max, 5ppm/ c drift ltc1391 8-channel multiplexer low r on : 45 w , low charge injection, serial interface lt1460 micropower series voltage reference 0.075% max, 10ppm/ c max drift, 2.5v, 5v and 10v versions ltc2400 24-bit m power, no latency ds adc in so-8 4ppm inl, 10ppm tue, 200 m a, pin compatible with LTC2420 ltc2401/ltc2402 1-/2-channel, 24-bit no latency ds adcs 24 bits in msop package ltc2404/ltc2408 4-/8-channel, 24-bit no latency ds adc 4ppm inl, 10ppm tue, 200 m a ltc2410 24-bit no latency ds adc with differential inputs 800nv noise, differential reference, 2.7v to 5.5v operation ltc2411 24-bit no latency ds adc with differential inputs/reference 1.6 m v noise, fully differential, 10-lead msop package ltc2413 24-bit no latency ds adc simultaneous 50hz to 60hz rejection 0.16ppm noise ltc2424/ltc2428 4-/8-channel 20-bit no latency ds adcs 8ppm inl, 1.2ppm noise, fast mode 2420f lt/lcg 1000 4k ? printed in usa ? linear technology corporation 2000 linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 l fax: (408) 434-0507 l www.linear-tech.com typical applicatio u the circuit shown in figure 41 enables pseudodifferential measurements of several bridge transducers and abso- lute temperature measurement. the ltc1391 is an 8-to-1 analog multiplexer. consecutive readings are performed on each side of the bridge by selecting the appropriate channel on the ltc1391. each output is digitized and the results digitally subtracted to obtain the pseudodifferential result. several bridge transducers may be digitized in this manner. in order to measure absolute temperature with a thermo- couple, cold junction compensation must be performed. channel 6 measures the output of the thermocouple while channel 7 measures the output of the cold junction sensor (diode, thermistor, etc.). this enables digital cold junc- tion compensation of the thermocouple output. the tem- perature measurement may then be used to compensate the temperature effects of the bridge transducers. ch1 ch0 thermocouple thermistor ch3 out gnd ltc1391 LTC2420 2420 f41 v ref v in gnd v cc v cc f o sck sdo cs ch4 ch5 ch6 ch7 ch2 figure 41. pseudodifferential multichannel bridge digitizer and digital cold junction compensation

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